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MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
Order this document by MC145151-2/D
PLL Frequency Synthesizer Family
CMOS
The devices described in this document are typically used as low-power, phase-locked loop frequency synthesizers. When combined with an external low-pass filter and voltage-controlled oscillator, these devices can provide all the remaining functions for a PLL frequency synthesizer operating up to the device's frequency limit. For higher VCO frequency operation, a down mixer or a prescaler can be used between the VCO and the synthesizer IC. These frequency synthesizer chips can be found in the following and other applications: CATV TV Tuning AM/FM Radios Scanning Receivers Two-Way Radios Amateur Radio
OSC
MC145151-2 MC145152-2 MC145155-2 MC145156-2 MC145157-2 MC145158-2
/R
CONTROL LOGIC
/A / P/P + 1
/N
VCO OUTPUT FREQUENCY
CONTENTS
Page DEVICE DETAIL SHEETS MC145151-2 Parallel-Input, Single-Modulus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 MC145152-2 Parallel-Input, Dual-Modulus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 MC145157-2 Serial-Input, Single-Modulus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 MC145158-2 Serial-Input, Dual-Modulus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 FAMILY CHARACTERISTICS Maximum Ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DC Electrical Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . AC Electrical Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Timing Requirements . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Frequency Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Phase Detector/Lock Detector Output Waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 15 17 18 19 19
DESIGN CONSIDERATIONS Phase-Locked Loop -- Low-Pass Filter Design . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 Crystal Oscillator Considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 Dual-Modulus Prescaling . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22
REV 4 12/99
(c) Motorola, Inc. 1999 MOTOROLA
MC145151-2 through MC145158-2
1
MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
MC145151-2 Parallel-Input PLL Frequency Synthesizer
Interfaces with Single-Modulus Prescalers
28
P SUFFIX PLASTIC DIP CASE 710
1
The MC145151-2 is programmed by 14 parallel-input data lines for the N counter and three input lines for the R counter. The device features consist of a reference oscillator, selectable-reference divider, digital-phase detector, and 14-bit programmable divide-by-N counter. The MC145151-2 is an improved-performance drop-in replacement for the MC145151-1. The power consumption has decreased and ESD and latch-up performance have improved. * * * * * * * * * * * * Operating Temperature Range: - 40 to 85C Low Power Consumption Through Use of CMOS Technology 3.0 to 9.0 V Supply Range On- or Off-Chip Reference Oscillator Operation Lock Detect Signal / N Counter Output Available Single Modulus/Parallel Programming 8 User-Selectable / R Values: 8, 128, 256, 512, 1024, 2048, 2410, 8192 / N Range = 3 to 16383 "Linearized" Digital Phase Detector Enhances Transfer Function Linearity Two Error Signal Options: Single-Ended (Three-State) or Double-Ended Chip Complexity: 8000 FETs or 2000 Equivalent Gates
28 1
DW SUFFIX SOG PACKAGE CASE 751F
ORDERING INFORMATION
MC145151P2 MC145151DW2 Plastic DIP SOG Package
PIN ASSIGNMENT
fin VSS VDD PDout RA0 RA1 RA2 R V fV N0 N1 N2 N3 1 2 3 4 5 6 7 8 9 10 11 12 13 14 28 27 26 25 24 23 22 21 20 19 18 17 16 15 LD OSCin OSCout N11 N10 N13 N12 T/R N9 N8 N7 N6 N5 N4
REV 1 8/95
(c) Motorola, Inc. 1995 MC145151-2 through MC145158-2
MOTOROLA
2
MC145151-2 BLOCK DIAGRAM
RA2 RA1 RA0
OSCout
14 x 8 ROM REFERENCE DECODER 14 LOCK DETECT LD
OSCin
14-BIT / R COUNTER PHASE DETECTOR A PDout
fin VDD
14-BIT / N COUNTER 14 PHASE DETECTOR B V R fV N13 N11 N9 N7 N6 N4 N2 N0
T/R
TRANSMIT OFFSET ADDER
NOTE: N0 - N13 inputs and inputs RA0, RA1, and RA2 have pull-up resistors that are not shown.
PIN DESCRIPTIONS
INPUT PINS fin Frequency Input (Pin 1) Input to the / N portion of the synthesizer. fin is typically derived from loop VCO and is ac coupled into the device. For larger amplitude signals (standard CMOS logic levels) dc coupling may be used. RA0 - RA2 Reference Address Inputs (Pins 5, 6, 7) These three inputs establish a code defining one of eight possible divide values for the total reference divider, as defined by the table below. Pull-up resistors ensure that inputs left open remain at a logic 1 and require only a SPST switch to alter data to the zero state.
Reference Address Code RA2 0 0 0 0 1 1 1 1 RA1 0 0 1 1 0 0 1 1 RA0 0 1 0 1 0 1 0 1 Total Divide Value 8 128 256 512 1024 2048 2410 8192
sure that inputs left open remain at a logic 1 and require only an SPST switch to alter data to the zero state. T/R Transmit/Receive Offset Adder Input (Pin 21) This input controls the offset added to the data provided at the N inputs. This is normally used for offsetting the VCO frequency by an amount equal to the IF frequency of the transceiver. This offset is fixed at 856 when T/R is low and gives no offset when T/R is high. A pull-up resistor ensures that no connection will appear as a logic 1 causing no offset addition. OSCin, OSCout Reference Oscillator Input/Output (Pins 27, 26) These pins form an on-chip reference oscillator when connected to terminals of an external parallel resonant crystal. Frequency setting capacitors of appropriate value must be connected from OSC in to ground and OSC out to ground. OSC in may also serve as the input for an externally-generated reference signal. This signal is typically ac coupled to OSC in, but for larger amplitude signals (standard CMOS logic levels) dc coupling may also be used. In the external reference mode, no connection is required to OSC out. OUTPUT PINS PDout Phase Detector A Output (Pin 4) Three-state output of phase detector for use as loop-error signal. Double-ended outputs are also available for this purpose (see V and R). Frequency fV > fR or fV Leading: Negative Pulses Frequency fV < fR or fV Lagging: Positive Pulses Frequency fV = fR and Phase Coincidence: High-Impedance State
N0 - N11 N Counter Programming Inputs (Pins 11 - 20, 22 - 25) These inputs provide the data that is preset into the / N counter when it reaches the count of zero. N0 is the least significant and N13 is the most significant. Pull-up resistors en-
MOTOROLA
MC145151-2 through MC145158-2
3
R , V Phase Detector B Outputs (Pins 8, 9) These phase detector outputs can be combined externally for a loop-error signal. A single-ended output is also available for this purpose (see PDout ). If frequency fV is greater than fR or if the phase of fV is leading, then error information is provided by V pulsing low. R remains essentially high. If the frequency fV is less than fR or if the phase of fV is lagging, then error information is provided by R pulsing low. V remains essentially high. If the frequency of fV = fR and both are in phase, then both V and R remain high except for a small minimum time period when both pulse low in phase. fV N Counter Output (Pin 10) This is the buffered output of the / N counter that is inter-
nally connected to the phase detector input. With this output available, the / N counter can be used independently. LD Lock Detector Output (Pin 28) Essentially a high level when loop is locked (fR, fV of same phase and frequency). Pulses low when loop is out of lock. POWER SUPPLY VDD Positive Power Supply (Pin 3) The positive power supply potential. This pin may range from + 3 to + 9 V with respect to VSS. VSS Negative Power Supply (Pin 2) The most negative supply potential. This pin is usually ground.
TYPICAL APPLICATIONS
2.048 MHz
NC
NC
OSCin
OSCout
fin MC145151-2
RA2 RA1
RA0 PDout VOLTAGE CONTROLLED OSCILLATOR 5 - 5.5 MHz
N13 N12 N11 N10 N9 N8 N7 N6 N5 N4 N3 N2 N1 N0
0 1 1 1 0 0 0 1 0 0 0 = 5 MHz 1 0 1 0 1 1 1 1 1 0 0 = 5.5 MHz
Figure 1. 5 MHz to 5.5 MHz Local Oscillator Channel Spacing = 1 kHz
LOCK DETECT SIGNAL "1" OSCout RA2 +V REF. OSC. 10.0417 MHz (ON-CHIP OSC. OPTIONAL) RECEIVE TRANSMIT (ADDS 856 TO / N VALUE) OSCin VDD VSS T/R "0" "0" "1" CHANNEL PROGRAMMING / N = 2284 TO 3484 "1" RA1 "0" RA0 LD fV PDout R fV fin CHOICE OF DETECTOR ERROR SIGNALS LOOP FILTER T: 13.0833 - 18.0833 MHz R: 9.5167 - 14.5167 MHz TRANSMIT: 440.0 - 470.0 MHz RECEIVE: 418.6 - 448.6 MHz (25 kHz STEPS)
MC145151-2
VCO
X6
T: 73.3333 - 78.3333 MHz R: 69.7667 - 74.7667 MHz DOWN MIXER
X6 60.2500 MHz NOTES: 1. fR = 4.1667 kHz; / R = 2410; 21.4 MHz low side injection during receive. 2. Frequency values shown are for the 440 - 470 MHz band. Similar implementation applies to the 406 - 440 MHz band. For 470 - 512 MHz, consider reference oscillator frequency X9 for mixer injection signal (90.3750 MHz).
Figure 2. Synthesizer for Land Mobile Radio UHF Bands
MC145151-2 Data Sheet Continued on Page 15
MC145151-2 through MC145158-2
MOTOROLA
4
MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
MC145152-2 Parallel-Input PLL Frequency Synthesizer
Interfaces with Dual-Modulus Prescalers
28
P SUFFIX PLASTIC DIP CASE 710
1
The MC145152-2 is programmed by sixteen parallel inputs for the N and A counters and three input lines for the R counter. The device features consist of a reference oscillator, selectable-reference divider, two-output phase detector, 10-bit programmable divide-by-N counter, and 6-bit programmable / A counter. The MC145152-2 is an improved-performance drop-in replacement for the MC145152-1. Power consumption has decreased and ESD and latch-up performance have improved. * * * * * * * * * * Operating Temperature Range: - 40 to 85C Low Power Consumption Through Use of CMOS Technology 3.0 to 9.0 V Supply Range On- or Off-Chip Reference Oscillator Operation Lock Detect Signal Dual Modulus/Parallel Programming 8 User-Selectable / R Values: 8, 64, 128, 256, 512, 1024, 1160, 2048 / N Range = 3 to 1023, / A Range = 0 to 63 Chip Complexity: 8000 FETs or 2000 Equivalent Gates See Application Note AN980
28 1
DW SUFFIX SOG PACKAGE CASE 751F
ORDERING INFORMATION
MC145152P2 MC145152DW2 Plastic DIP SOG Package
PIN ASSIGNMENT
fin VSS VDD RA0 RA1 RA2 R V MC A5 N0 N1 N2 N3 1 2 3 4 5 6 7 8 9 10 11 12 13 14 28 27 26 25 24 23 22 21 20 19 18 17 16 15 LD OSCin OSCout A4 A3 A0 A2 A1 N9 N8 N7 N6 N5 N4
REV 1 8/95
(c) Motorola, Inc. 1995 MOTOROLA
MC145151-2 through MC145158-2
5
MC145152-2 BLOCK DIAGRAM
RA2 RA1 RA0
12 x 8 ROM REFERENCE DECODER 12
OSCout
OSCin
12-BIT / R COUNTER
LOCK DETECT
LD MC
CONTROL LOGIC fin 6-BIT / A COUNTER A5 A3 A2 A0 N0 10-BIT / N COUNTER N2 N4 N5 N7 N9
PHASE DETECTOR
V R
NOTE: N0 - N9, A0 - A5, and RA0 - RA2 have pull-up resistors that are not shown.
PIN DESCRIPTIONS
INPUT PINS fin Frequency Input (Pin 1) Input to the positive edge triggered / N and / A counters. fin is typically derived from a dual-modulus prescaler and is ac coupled into the device. For larger amplitude signals (standard CMOS logic levels) dc coupling may be used. RA0, RA1, RA2 Reference Address Inputs (Pins 4, 5, 6) These three inputs establish a code defining one of eight possible divide values for the total reference divider. The total reference divide values are as follows:
Reference Address Code RA2 0 0 0 0 1 1 1 1 RA1 0 0 1 1 0 0 1 1 RA0 0 1 0 1 0 1 0 1 Total Divide Value 8 64 128 256 512 1024 1160 2048
Prescaling section). The A inputs all have internal pull-up resistors that ensure that inputs left open will remain at a logic 1. OSCin, OSCout Reference Oscillator Input/Output (Pins 27, 26) These pins form an on-chip reference oscillator when connected to terminals of an external parallel resonant crystal. Frequency setting capacitors of appropriate value must be connected from OSC in to ground and OSC out to ground. OSC in may also serve as the input for an externally-generated reference signal. This signal is typically ac coupled to OSC in, but for larger amplitude signals (standard CMOS logic levels) dc coupling may also be used. In the external reference mode, no connection is required to OSCout. OUTPUT PINS R , V Phase Detector B Outputs (Pins 7, 8) These phase detector outputs can be combined externally for a loop-error signal. If the frequency fV is greater than fR or if the phase of fV is leading, then error information is provided by V pulsing low. R remains essentially high. If the frequency fV is less than fR or if the phase of fV is lagging, then error information is provided by R pulsing low. V remains essentially high. If the frequency of fV = fR and both are in phase, then both V and R remain high except for a small minimum time period when both pulse low in phase. MC Dual-Modulus Prescale Control Output (Pin 9) Signal generated by the on-chip control logic circuitry for controlling an external dual-modulus prescaler. The MC level will be low at the beginning of a count cycle and will remain low until the / A counter has counted down from its programmed value. At this time, MC goes high and remains high until the / N counter has counted the rest of the way down from its programmed value (N - A additional counts since both / N and / A are counting down during the first
N0 - N9 N Counter Programming Inputs (Pins 11 - 20) The N inputs provide the data that is preset into the / N counter when it reaches the count of 0. N0 is the least significant digit and N9 is the most significant. Pull-up resistors ensure that inputs left open remain at a logic 1 and require only a SPST switch to alter data to the zero state. A0 - A5 A Counter Programming Inputs (Pins 23, 21, 22, 24, 25, 10) The A inputs define the number of clock cycles of fin that require a logic 0 on the MC output (see Dual-Modulus MC145151-2 through MC145158-2
MOTOROLA
6
portion of the cycle). MC is then set back low, the counters preset to their respective programmed values, and the above sequence repeated. This provides for a total programmable divide value (NT) = N * P + A where P and P + 1 represent the dual-modulus prescaler divide values respectively for high and low MC levels, N the number programmed into the / N counter, and A the number programmed into the / A counter. LD Lock Detector Output (Pin 28) Essentially a high level when loop is locked (fR, fV of same phase and frequency). Pulses low when loop is out of lock.
POWER SUPPLY VDD Positive Power Supply (Pin 3) The positive power supply potential. This pin may range from + 3 to + 9 V with respect to VSS. VSS Negative Power Supply (Pin 2) The most negative supply potential. This pin is usually ground.
TYPICAL APPLICATIONS
NO CONNECTS "1" 10.24 MHz NOTE 1 OSCout OSCin MC145152-2 +V VDD VSS N9 N0 A5 MC fin A0 RA2 RA1 RA0 LD R V R1 - R1 + R2 C MC33171 NOTE 2 VCO "1" "1" 150 - 175 MHz 5 kHz STEPS
LOCK DETECT SIGNAL R2 C
CHANNEL PROGRAMMING
MC12017 / 64/65 PRESCALER
NOTES: 1. Off-chip oscillator optional. 2. The R and V outputs are fed to an external combiner/loop filter. See the Phase-Locked Loop -- Low-Pass Filter Design page for additional information. The R and V outputs swing rail-to-rail. Therefore, the user should be careful not to exceed the common mode input range of the op amp used in the combiner/loop filter.
Figure 1. Synthesizer for Land Mobile Radio VHF Bands
MOTOROLA
MC145151-2 through MC145158-2
7
REF. OSC. 15.360 MHz (ON-CHIP OSC. OPTIONAL)
NO CONNECTS X2 "1" "1" "1"
RECEIVER 2ND L.O. 30.720 MHz LOCK DETECT SIGNAL R2 C RECEIVER FIRST L.O. 825.030 844.980 MHz (30 kHz STEPS)
OSCout OSCin +V VDD VSS N9
RA2
RA1
RA0
LD R V MC fin
R1 - R1 + NOTE 7 R2 C TRANSMITTER MODULATION MC12017 / 64/65 PRESCALER NOTE 6 X4 NOTE 6 VCO X4 NOTE 6
MC145152-2 NOTE 5
N0 A5
A0
CHANNEL PROGRAMMING
NOTES: 1. Receiver 1st I.F. = 45 MHz, low side injection; Receiver 2nd I.F. = 11.7 MHz, low side injection. 2. Duplex operation with 45 MHz receiver/transmit separation. 3. fR = 7.5 kHz; / R = 2048. 4. Ntotal = N + A = 27501 to 28166; N = 429 to 440; A = 0 to 63. 64 5. MC145158-2 may be used where serial data entry is desired. 6. High frequency prescalers (e.g., MC12018 [520 MHz] and MC12022 [1 GHz]) may be used for higher frequency VCO and fref implementations. 7. The R and V outputs are fed to an external combiner/loop filter. See the Phase-Locked Loop -- Low-Pass Filter Design page for additional information. The R and V outputs swing rail-to-rail. Therefore, the user should be careful not to exceed the common mode input range of the op amp used in the combiner/loop filter.
TRANSMITTER SIGNAL 825.030 844.980 MHz (30 kHz STEPS)
Figure 2. 666-Channel, Computer-Controlled, Mobile Radiotelephone Synthesizer for 800 MHz Cellular Radio Systems
MC145152-2 Data Sheet Continued on Page 15
MC145151-2 through MC145158-2
MOTOROLA
8
MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
MC145157-2 Serial-Input PLL Frequency Synthesizer
Interfaces with Single-Modulus Prescalers
16
P SUFFIX PLASTIC DIP CASE 648
1
The MC145157-2 has a fully programmable 14-bit reference counter, as well as a fully programmable / N counter. The counters are programmed serially through a common data input and latched into the appropriate counter latch, according to the last data bit (control bit) entered. The MC145157-2 is an improved-performance drop-in replacement for the MC145157-1. Power consumption has decreased and ESD and latch-up performance have improved. * * * * * * * * * * * * Operating Temperature Range: - 40 to 85C Low Power Consumption Through Use of CMOS Technology 3.0 to 9.0 V Supply Range Fully Programmable Reference and / N Counters / R Range = 3 to 16383 / N Range = 3 to 16383 fV and fR Outputs Lock Detect Signal Compatible with the Serial Peripheral Interface (SPI) on CMOS MCUs "Linearized" Digital Phase Detector Single-Ended (Three-State) or Double-Ended Phase Detector Outputs Chip Complexity: 6504 FETs or 1626 Equivalent Gates
16 1
DW SUFFIX SOG PACKAGE CASE 751G
ORDERING INFORMATION
MC145157P2 MC145157DW2 Plastic DIP SOG Package
PIN ASSIGNMENT
OSCin OSCout fV VDD PDout VSS LD fin 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 R V REFout fR S/Rout ENB DATA CLK
REV 1 8/95
(c) Motorola, Inc. 1995 MOTOROLA
MC145151-2 through MC145158-2
9
MC145157-2 BLOCK DIAGRAM
14-BIT SHIFT REGISTER 14 ENB REFERENCE COUNTER LATCH 14 OSCin OSCout REFout 14-BIT / R COUNTER PHASE DETECTOR A PDout LOCK DETECT LD fR
fin
14-BIT / N COUNTER 14
PHASE DETECTOR B
V R
/ N COUNTER LATCH
DATA 1-BIT CONTROL S/R 14 14-BIT SHIFT REGISTER
fV
S/Rout
CLK
PIN DESCRIPTIONS
INPUT PINS fin Frequency Input (Pin 8) Input frequency from VCO output. A rising edge signal on this input decrements the / N counter. This input has an inverter biased in the linear region to allow use with ac coupled signals as low as 500 mV p-p. For larger amplitude signals (standard CMOS logic levels), dc coupling may be used. CLK, DATA Shift Clock, Serial Data Inputs (Pins 9, 10) Each low-to-high transition of the clock shifts one bit of data into the on-chip shift registers. The last data bit entered determines which counter storage latch is activated; a logic 1 selects the reference counter latch and a logic 0 selects the / N counter latch. The entry format is as follows:
CONTROL MSB LSB
if the control bit is at a logic low. A logic low on this pin allows the user to change the data in the shift registers without affecting the counters. ENB is normally low and is pulsed high to transfer data to the latches. OSCin, OSCout Reference Oscillator Input/Output (Pins 1, 2) These pins form an on-chip reference oscillator when connected to terminals of an external parallel resonant crystal. Frequency setting capacitors of appropriate value must be connected from OSC in to ground and OSC out to ground. OSC in may also serve as the input for an externally-generated reference signal. This signal is typically ac coupled to OSC in, but for larger amplitude signals (standard CMOS logic levels) dc coupling may also be used. In the external reference mode, no connection is required to OSC out. OUTPUT PINS PDout Single-Ended Phase Detector A Output (Pin 5) This single-ended (three-state) phase detector output produces a loop-error signal that is used with a loop filter to control a VCO. Frequency fV > fR or fV Leading: Negative Pulses Frequency fV < fR or fV Lagging: Positive Pulses Frequency fV = fR and Phase Coincidence: High-Impedance State R , V Double-Ended Phase Detector B Outputs (Pins 16, 15) These outputs can be combined externally for a loop-error signal. A single-ended output is also available for this purpose (see PDout ).
FIRST DATA BIT INTO SHIFT REGISTER
ENB Latch Enable Input (Pin 11) A logic high on this pin latches the data from the shift register into the reference divider or / N latches depending on the control bit. The reference divider latches are activated if the control bit is at a logic high and the / N latches are activated
MC145151-2 through MC145158-2
MOTOROLA
10
If frequency fV is greater than fR or if the phase of fV is leading, then error information is provided by V pulsing low. R remains essentially high. If the frequency fV is less than fR or if the phase of fV is lagging, then error information is provided by R pulsing low. V remains essentially high. If the frequency of fV = fR and both are in phase, then both V and R remain high except for a small minimum time period when both pulse low in phase. f R , fV R Counter Output, N Counter Output (Pins 13, 3) Buffered, divided reference and fin frequency outputs. The fR and fV outputs are connected internally to the / R and / N counter outputs respectively, allowing the counters to be used independently, as well as monitoring the phase detector inputs. LD Lock Detector Output (Pin 7) This output is essentially at a high level when the loop is locked (fR, fV of same phase and frequency), and pulses low when loop is out of lock.
REFout Buffered Reference Oscillator Output (Pin 14) This output can be used as a second local oscillator, reference oscillator to another frequency synthesizer, or as the system clock to a microprocessor controller. S/Rout Shift Register Output (Pin 12) This output can be connected to an external shift register to provide band switching, control information, and counter programming code checking. POWER SUPPLY VDD Positive Power Supply (Pin 4) The positive power supply potential. This pin may range from + 3 to + 9 V with respect to VSS. VSS Negative Power Supply (Pin 6) The most negative supply potential. This pin is usually ground.
MC145157-2 Data Sheet Continued on Page 15
MOTOROLA
MC145151-2 through MC145158-2
11
MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
MC145158-2 Serial-Input PLL Frequency Synthesizer
Interfaces with Dual-Modulus Prescalers
16
P SUFFIX PLASTIC DIP CASE 648
1
The MC145158-2 has a fully programmable 14-bit reference counter, as well as fully programmable / N and / A counters. The counters are programmed serially through a common data input and latched into the appropriate counter latch, according to the last data bit (control bit) entered. The MC145158-2 is an improved-performance drop-in replacement for the MC145158-1. Power consumption has decreased and ESD and latch-up performance have improved. * * * * * * * * * * * * * Operating Temperature Range: - 40 to 85C Low Power Consumption Through Use of CMOS Technology 3.0 to 9.0 V Supply Range Fully Programmable Reference and / N Counters / R Range = 3 to 16383 / N Range = 3 to 1023 Dual Modulus Capability; / A Range = 0 to 127 fV and fR Outputs Lock Detect Signal Compatible with the Serial Peripheral Interface (SPI) on CMOS MCUs "Linearized" Digital Phase Detector Single-Ended (Three-State) or Double-Ended Phase Detector Outputs Chip Complexity: 6504 FETs or 1626 Equivalent Gates
16 1
DW SUFFIX SOG PACKAGE CASE 751G
ORDERING INFORMATION
MC145158P2 MC145158DW2 Plastic DIP SOG Package
PIN ASSIGNMENT
OSCin OSCout fV VDD PDout VSS LD fin 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 R V REFout fR MC ENB DATA CLK
REV 1 8/95
(c) Motorola, Inc. 1995 MC145151-2 through MC145158-2
MOTOROLA
12
MC145158-2 BLOCK DIAGRAM
14-BIT SHIFT REGISTER 14 ENB REFERENCE COUNTER LATCH 14 OSCin OSCout REFout 7-BIT / A COUNTER 7 CONTROL LOGIC 14-BIT / R COUNTER PHASE DETECTOR A PDout LOCK DETECT LD fR
fin
10-BIT / N COUNTER 10
PHASE DETECTOR B
V R
/ A COUNTER
LATCH DATA 1-BIT CONTROL S/R 7 7-BIT S/R
/ N COUNTER
LATCH 10 10-BIT S/R
fV
MC
CLK
PIN DESCRIPTIONS
INPUT PINS fin Frequency Input (Pin 8) Input frequency from VCO output. A rising edge signal on this input decrements the / A and / N counters. This input has an inverter biased in the linear region to allow use with ac coupled signals as low as 500 mV p-p. For larger amplitude signals (standard CMOS logic levels), dc coupling may be used. CLK, DATA Shift Clock, Serial Data Inputs (Pins 9, 10) Each low-to-high transition of the CLK shifts one bit of data into the on-chip shift registers. The last data bit entered determines which counter storage latch is activated; a logic 1 selects the reference counter latch and a logic 0 selects the / A, / N counter latch. The data entry format is as follows:
CONTROL LSB
/A
MSB LSB
/N
MSB
FIRST DATA BIT INTO SHIFT REGISTER
ENB Latch Enable Input (Pin 11) A logic high on this pin latches the data from the shift register into the reference divider or / N, / A latches depending on the control bit. The reference divider latches are activated if the control bit is at a logic high and the / N, / A latches are activated if the control bit is at a logic low. A logic low on this pin allows the user to change the data in the shift registers without affecting the counters. ENB is normally low and is pulsed high to transfer data to the latches. OSCin, OSCout Reference Oscillator Input/Output (Pins 1, 2) These pins form an on-chip reference oscillator when connected to terminals of an external parallel resonant crystal. Frequency setting capacitors of appropriate value must be connected from OSC in to ground and OSC out to ground. OSC in may also serve as the input for an externally-generated reference signal. This signal is typically ac coupled to OSCin, but for larger amplitude signals (standard CMOS logic levels) dc coupling may also be used. In the external reference mode, no connection is required to OSC out.
/R
CONTROL MSB FIRST DATA BIT INTO SHIFT REGISTER LSB
MOTOROLA
MC145151-2 through MC145158-2
13
OUTPUT PINS PDout Phase Detector A Output (Pin 5) This single-ended (three-state) phase detector output produces a loop-error signal that is used with a loop filter to control a VCO. Frequency fV > fR or fV Leading: Negative Pulses Frequency fV < fR or fV Lagging: Positive Pulses Frequency fV = fR and Phase Coincidence: High-Impedance State R , V Phase Detector B Outputs (Pins 16, 15) Double-ended phase detector outputs. These outputs can be combined externally for a loop-error signal. A single- ended output is also available for this purpose (see PDout ). If frequency fV is greater than fR or if the phase of fV is leading, then error information is provided by V pulsing low. R remains essentially high. If the frequency fV is less than fR or if the phase of fV is lagging, then error information is provided by R pulsing low. V remains essentially high. If the frequency of fV = fR and both are in phase, then both V and R remain high except for a small minimum time period when both pulse low in phase. MC Dual-Modulus Prescale Control Output (Pin 12) This output generates a signal by the on-chip control logic circuitry for controlling an external dual-modulus prescaler. The MC level is low at the beginning of a count cycle and remains low until the / A counter has counted down from its programmed value. At this time, MC goes high and remains high until the / N counter has counted the rest of the way down from its programmed value (N - A additional counts since both / N and / A are counting down during the first portion of the cycle). MC is then set back low, the counters preset to their respective programmed values, and the above sequence repeated. This provides for a total programmable divide value (NT) = N P + A where P and P + 1 represent the
dual-modulus prescaler divide values respectively for high and low modulus control levels, N the number programmed into the / N counter, and A the number programmed into the / A counter. Note that when a prescaler is needed, the dual- modulus version offers a distinct advantage. The dual- modulus prescaler allows a higher reference frequency at the phase detector input, increasing system performance capability, and simplifying the loop filter design. f R , fV R Counter Output, N Counter Output (Pins 13, 3) Buffered, divided reference and fin frequency outputs. The fR and fV outputs are connected internally to the / R and / N counter outputs respectively, allowing the counters to be used independently, as well as monitoring the phase detector inputs. LD Lock Detector Output (Pin 7) This output is essentially at a high level when the loop is locked (fR, fV of same phase and frequency), and pulses low when loop is out of lock. REFout Buffered Reference Oscillator Output (Pin 14) This output can be used as a second local oscillator, reference oscillator to another frequency synthesizer, or as the system clock to a microprocessor controller. POWER SUPPLY VDD Positive Power Supply (Pin 4) The positive power supply potential. This pin may range from + 3 to + 9 V with respect to VSS. VSS Negative Power Supply (Pin 6) The most negative supply potential. This pin is usually ground.
MC145151-2 through MC145158-2
MOTOROLA
14
MC14515X-2 FAMILY CHARACTERISTICS AND DESCRIPTIONS
MAXIMUM RATINGS* (Voltages Referenced to VSS)
Symbol VDD Vin, Vout Vout Iin, Iout IDD, ISS PD Tstg TL Parameter DC Supply Voltage Input or Output Voltage (DC or Transient) except SW1, SW2 Output Voltage (DC or Transient), SW1, SW2 (Rpull-up = 4.7 k) Input or Output Current (DC or Transient), per Pin Supply Current, VDD or VSS Pins Power Dissipation, per Package Storage Temperature Lead Temperature, 1 mm from Case for 10 seconds Value - 0.5 to + 10.0 - 0.5 to VDD + 0.5 - 0.5 to + 15 10 30 500 - 65 to + 150 260 Unit V V V mA mA mW C C These devices contain protection circuitry to protect against damage due to high static voltages or electric fields. However, precautions must be taken to avoid applications of any voltage higher than maximum rated voltages to these high-impedance circuits. For proper operation, Vin and Vout should be constrained to the range VSS (Vin or Vout) VDD except for SW1 and SW2. SW1 and SW2 can be tied through external resistors to voltages as high as 15 V, independent of the supply voltage. Unused inputs must always be tied to an appropriate logic voltage level (e.g., either VSS or VDD), except for inputs with pull-up devices. Unused outputs must be left open.
* Maximum Ratings are those values beyond which damage to the device may occur. Functional operation should be restricted to the limits in the Electrical Characteristics tables or Pin Descriptions section. Power Dissipation Temperature Derating: Plastic DIP: - 12 mW/C from 65 to 85C SOG Package: - 7 mW/C from 65 to 85C
ELECTRICAL CHARACTERISTICS (Voltages Referenced to VSS)
Symbol VDD Iss Parameter Power Supply Voltage Range Dynamic Supply Current fin = OSCin = 10 MHz, 1 V p-p ac coupled sine wave R = 128, A = 32, N = 128 Vin = VDD or VSS Iout = 0 A Input ac coupled sine wave Vout 2.1 V Vout 3.5 V Vout 6.3 V Vout 0.9 V Vout 1.5 V Vout 2.7 V Input dc coupled square wave Input dc coupled square wave Test Condition VDD V -- 3 5 9 3 5 9 -- 3 5 9 3 5 9 3 5 9 3 5 9 Vin = VDD or VSS Vin = VSS 9 9 - 40C Min 3 -- -- -- -- -- -- 500 -- -- -- 3.0 5.0 9.0 -- -- -- 2.1 3.5 6.3 2 -- Max 9 3.5 10 30 800 1200 1600 -- 0 0 0 -- -- -- 0.9 1.5 2.7 -- -- -- 50 - 0.3 25C Min 3 -- -- -- -- -- -- 500 -- -- -- 3.0 5.0 9.0 -- -- -- 2.1 3.5 6.3 2 -- Max 9 3 7.5 24 800 1200 1600 -- 0 0 0 -- -- -- 0.9 1.5 2.7 -- -- -- 25 - 0.1 85C Min 3 -- -- -- -- -- -- 500 -- -- -- 3.0 5.0 9.0 -- -- -- 2.1 3.5 6.3 2 -- Max 9 3 7.5 24 1600 2400 3200 -- 0 0 0 -- -- -- 0.9 1.5 2.7 -- -- -- 22 - 1.0 Unit V mA
ISS
Quiescent Supply Current (not including pull-up current component) Input Voltage -- fin, OSCin Low-Level Input Voltage -- fin, OSCin High-Level Input Voltage -- fin, OSCin Low-Level Input Voltage -- except fin, OSCin High-Level Input Voltage -- except fin, OSCin Input Current (fin, OSCin) Input Leakage Current (Data, CLK, ENB -- without pull-ups) Input Leakage Current (all inputs except fin, OSCin)
A
Vin VIL
mV p-p V
VIH
V
VIL
V
VIH
V
Iin IIL
A A
IIH
Vin = VDD
9
--
0.3
--
0.1
--
1.0
A (continued)
MOTOROLA
MC145151-2 through MC145158-2
15
DC ELECTRICAL CHARACTERISTICS (continued)
VDD V 9 -- Iout 0 A Vin = VDD Iout 0 A Vin = VSS Iout 0 A 3 5 9 3 5 9 3 5 9 3 5 9 -- - 40C Min - 20 -- -- -- -- 2.1 3.5 6.3 -- -- -- 2.95 4.95 8.95 15 Max - 400 10 0.9 1.5 2.7 -- -- -- 0.05 0.05 0.05 -- -- -- -- 25C Min - 20 -- -- -- -- 2.1 3.5 6.3 -- -- -- 2.95 4.95 8.95 15 Max - 200 10 0.9 1.5 2.7 -- -- -- 0.05 0.05 0.05 -- -- -- -- 85C Min - 20 -- -- -- -- 2.1 3.5 6.3 -- -- -- 2.95 4.95 8.95 15 Max - 170 10 0.9 1.5 2.7 -- -- -- 0.05 0.05 0.05 -- -- -- -- Unit A pF V
Symbol IIL Cin VOL
Parameter Pull-up Current (all inputs with pull-ups) Input Capacitance Low-Level Output Voltage -- OSCout High-Level Output Voltage -- OSCout Low-Level Output Voltage -- Other Outputs High-Level Output Voltage -- Other Outputs Drain-to-Source Breakdown Voltage -- SW1, SW2 Low-Level Sinking Current -- MC High-Level Sourcing Current -- MC Low-Level Sinking Current -- LD High-Level Sourcing Current -- LD Low-Level Sinking Current -- SW1, SW2 Low-Level Sinking Current -- Other Outputs High-Level Sourcing Current -- Other Outputs Output Leakage Current -- PDout Output Leakage Current -- SW1, SW2 Output Capacitance -- PDout
Test Condition Vin = VSS
VOH
V
VOL
V
VOH
Iout 0 A
V
V(BR)DSS
Rpull-up = 4.7 k
V
IOL
Vout = 0.3 V Vout = 0.4 V Vout = 0.5 V Vout = 2.7 V Vout = 4.6 V Vout = 8.5 V Vout = 0.3 V Vout = 0.4 V Vout = 0.5 V Vout = 2.7 V Vout = 4.6 V Vout = 8.5 V Vout = 0.3 V Vout = 0.4 V Vout = 0.5 V Vout = 0.3 V Vout = 0.4 V Vout = 0.5 V Vout = 2.7 V Vout = 4.6 V Vout = 8.5 V Vout = VDD or VSS Output in Off State Vout = VDD or VSS Output in Off State PDout -- Three-State
3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 9 9 --
1.30 1.90 3.80 - 0.60 - 0.90 - 1.50 0.25 0.64 1.30 - 0.25 - 0.64 - 1.30 0.80 1.50 3.50 0.44 0.64 1.30 - 0.44 - 0.64 - 1.30 -- -- --
-- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- 0.3 0.3 10
1.10 1.70 3.30 - 0.50 - 0.75 - 1.25 0.20 0.51 1.00 - 0.20 - 0.51 - 1.00 0.48 0.90 2.10 0.35 0.51 1.00 - 0.35 - 0.51 - 1.00 -- -- --
-- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- 0.1 0.1 10
0.66 1.08 2.10 - 0.30 - 0.50 - 0.80 0.15 0.36 0.70 - 0.15 - 0.36 - 0.70 0.24 0.45 1.05 0.22 0.36 0.70 - 0.22 - 0.36 - 0.70 -- -- --
-- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- -- 1.0 3.0 10
mA
IOH
mA
IOL
mA
IOH
mA
IOL
mA
IOL
mA
IOH
mA
IOZ IOZ Cout
A A pF
MC145151-2 through MC145158-2
MOTOROLA
16
AC ELECTRICAL CHARACTERISTICS (CL = 50 pF, Input tr = tf = 10 ns)
Symbol tPLH, tPHL Parameter Maximum Propagation Delay, fin to MC (Figures 1 and 4) Maximum Propagation Delay, ENB to SW1, SW2 (Figures 1 and 5) Output Pulse Width, R, V, and LD with fR in Phase with fV (Figures 2 and 4) Maximum Output Transition Time, MC (Figures 3 and 4) Maximum Output Transition Time, MC (Figures 3 and 4) Maximum Output Transition Time, LD (Figures 3 and 4) Maximum Output Transition Time, Other Outputs (Figures 3 and 4) VDD V 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 Guaranteed Limit 25C 110 60 35 160 80 50 25 to 200 20 to 100 10 to 70 115 60 40 60 34 30 180 90 70 160 80 60 Guaranteed Limit - 40 to 85C 120 70 40 180 95 60 25 to 260 20 to 125 10 to 80 115 75 60 70 45 38 200 120 90 175 100 65 Unit ns
tPHL
ns
tw
ns
tTLH
ns
tTHL
ns
tTLH, tTHL
ns
tTLH, tTHL
ns
SWITCHING WAVEFORMS
INPUT 50% tPLH OUTPUT 50% tPHL VDD -- VSS R, V, LD* 50% tw
* fR in phase with fV.
Figure 1.
Figure 2.
tTLH ANY OUTPUT 90% 10%
tTHL
Figure 3.
VDD TEST POINT OUTPUT DEVICE UNDER TEST DEVICE UNDER TEST TEST POINT OUTPUT 15 k
CL*
CL*
* Includes all probe and fixture capacitance.
* Includes all probe and fixture capacitance.
Figure 4. Test Circuit
Figure 5. Test Circuit
MOTOROLA
MC145151-2 through MC145158-2
17
TIMING REQUIREMENTS (Input tr = tf = 10 ns unless otherwise indicated)
Symbol fclk Parameter Serial Data Clock Frequency, Assuming 25% Duty Cycle NOTE: Refer to CLK tw(H) below (Figure 6) Minimum Setup Time, Data to CLK (Figure 7) Minimum Hold Time, CLK to Data (Figure 7) Minimum Setup Time, CLK to ENB (Figure 7) Minimum Recovery Time, ENB to CLK (Figure 7) Minimum Pulse Width, CLK and ENB (Figure 6) Maximum Input Rise and Fall Times -- Any Input (Figure 8) VDD V 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 3 5 9 Guaranteed Limit 25C dc to 5.0 dc to 7.1 dc to 10 30 20 18 40 20 15 70 32 25 5 10 20 50 35 25 5 4 2 Guaranteed Limit - 40 to 85C dc to 3.5 dc to 7.1 dc to 10 30 20 18 40 20 15 70 32 25 5 10 20 70 35 25 5 4 2 Unit MHz
tsu
ns
th
ns
tsu
ns
trec
ns
tw(H)
ns
tr, tf
s
SWITCHING WAVEFORMS
tw(H) CLK, ENB -- VDD 50% 1* 4 fclk VSS CLK 50% -- VDD DATA tsu 50% VSS th -- VDD LAST CLK tsu 50% VSS tt ANY OUTPUT 90% 10% tf -- VDD VSS PREVIOUS DATA LATCHED FIRST CLK trec -- VDD ENB VSS
*Assumes 25% Duty Cycle.
Figure 6.
Figure 7.
Figure 8.
MC145151-2 through MC145158-2
MOTOROLA
18
FREQUENCY CHARACTERISTICS (Voltages References to VSS, CL = 50 pF, Input tr = tf =10 ns unless otherwise indicated)
Symbol fi Parameter Input Frequency (fin, OSCin) Test Condition R 8, A 0, N 8 Vin = 500 mV p-p ac coupled sine wave R 8, A 0, N 8 Vin = 1 V p-p ac coupled sine wave R 8, A 0, N 8 Vin = VDD to VSS dc coupled square wave VDD V 3 5 9 3 5 9 3 5 9 - 40C Min -- -- -- -- -- -- -- -- -- Max 6 15 15 12 22 25 13 25 25 25C Min -- -- -- -- -- -- -- -- -- Max 6 15 15 12 20 22 12 22 25 85C Min -- -- -- -- -- -- -- -- -- Max 6 15 15 7 20 22 8 22 25 Unit MHz
MHz
MHz
NOTE: Usually, the PLL's propagation delay from fin to MC plus the setup time of the prescaler determines the upper frequency limit of the system. The upper frequency limit is found with the following formula: f = P / (tP + tset) where f is the upper frequency in Hz, P is the lower of the dual modulus prescaler ratios, tP is the fin to MC propagation delay in seconds, and tset is the prescaler setup time in seconds. For example, with a 5 V supply, the fin to MC delay is 70 ns. If the MC12028A prescaler is used, the setup time is 16 ns. Thus, if the 64/65 ratio is utilized, the upper frequency limit is f = P / (tP + tset) = 64/(70 + 16) = 744 MHz.
fR REFERENCE OSC / R fV FEEDBACK (fin / N)
VH VL VH VL VH HIGH IMPEDANCE VL VH
*
PDout
R V VL VH VL VH LD VL VH = High Voltage Level. VL = Low Voltage Level. * At this point, when both fR and fV are in phase, the output is forced to near mid-supply. NOTE: The PDout generates error pulses during out-of-lock conditions. When locked in phase and frequency the output is high and the voltage at this pin is determined by the low-pass filter capacitor.
Figure 9. Phase Detector/Lock Detector Output Waveforms
MOTOROLA
MC145151-2 through MC145158-2
19
DESIGN CONSIDERATIONS
PHASE-LOCKED LOOP -- LOW-PASS FILTER DESIGN
A) KKVCO NR1C Nn 2KKVCO 1 R1sC + 1 KKVCO NC(R1 + R2) R2C + N KKVCO
PDout R -- V --
VCO R1 C
n = = F(s) =
B)
PDout R -- V --
VCO R1 R2 C
n =
= 0.5 n
F(s) =
R2sC + 1 (R1 + R2)sC + 1
C)
PDout -- R V R1
R2 _ +A R1 R2 C C VCO n = =
KKVCO NCR1 nR2C 2
ASSUMING GAIN A IS VERY LARGE, THEN: F(s) = R2sC + 1 R1sC
NOTE: Sometimes R1 is split into two series resistors, each R1 / 2. A capacitor CC is then placed from the midpoint to ground to further filter V and R. The value of CC should be such that the corner frequency of this network does not significantly affect n. The R and V outputs swing rail-to-rail. Therefore, the user should be careful not to exceed the common mode input range of the op amp used in the combiner/loop filter. DEFINITIONS: N = Total Division Ratio in feedback loop K (Phase Detector Gain) = VDD/4 for PDout K (Phase Detector Gain) = VDD/2 for V and R 2fVCO KVCO (VCO Gain) = VVCO
for a typical design wn (Natural Frequency) 2fr (at phase detector input). 10 Damping Factor: 1
RECOMMENDED READING: Gardner, Floyd M., Phaselock Techniques (second edition). New York, Wiley-Interscience, 1979. Manassewitsch, Vadim, Frequency Synthesizers: Theory and Design (second edition). New York, Wiley-Interscience, 1980. Blanchard, Alain, Phase-Locked Loops: Application to Coherent Receiver Design. New York, Wiley-Interscience, 1976. Egan, William F., Frequency Synthesis by Phase Lock. New York, Wiley-Interscience, 1981. Rohde, Ulrich L., Digital PLL Frequency Synthesizers Theory and Design. Englewood Cliffs, NJ, Prentice-Hall, 1983. Berlin, Howard M., Design of Phase-Locked Loop Circuits, with Experiments. Indianapolis, Howard W. Sams and Co., 1978. Kinley, Harold, The PLL Synthesizer Cookbook. Blue Ridge Summit, PA, Tab Books, 1980. AN535, Phase-Locked Loop Design Fundamentals, Motorola Semiconductor Products, Inc., 1970. AR254, Phase-Locked Loop Design Articles, Motorola Semiconductor Products, Inc., Reprinted with permission from Electronic Design, 1987.
MC145151-2 through MC145158-2
MOTOROLA
20
CRYSTAL OSCILLATOR CONSIDERATIONS The following options may be considered to provide a reference frequency to Motorola's CMOS frequency synthesizers. Use of a Hybrid Crystal Oscillator Commercially available temperature-compensated crystal oscillators (TCXOs) or crystal-controlled data clock oscillators provide very stable reference frequencies. An oscillator capable of sinking and sourcing 50 A at CMOS logic levels may be direct or dc coupled to OSCin. In general, the highest frequency capability is obtained utilizing a direct-coupled square wave having a rail-to-rail (VDD to VSS) voltage swing. If the oscillator does not have CMOS logic levels on the outputs, capacitive or ac coupling to OSCin may be used. OSCout, an unbuffered output, should be left floating. For additional information about TCXOs and data clock oscillators, please consult the latest version of the eem Electronic Engineers Master Catalog, the Gold Book, or similar publications. Design an Off-Chip Reference The user may design an off-chip crystal oscillator using ICs specifically developed for crystal oscillator applications, such as the MC12061 MECL device. The reference signal from the MECL device is ac coupled to OSCin. For large amplitude signals (standard CMOS logic levels), dc coupling is used. OSCout, an unbuffered output, should be left floating. In general, the highest frequency capability is obtained with a direct-coupled square wave having rail-to-rail voltage swing. Use of the On-Chip Oscillator Circuitry The on-chip amplifier (a digital inverter) along with an appropriate crystal may be used to provide a reference source frequency. A fundamental mode crystal, parallel resonant at the desired operating frequency, should be connected as shown in Figure 10.
Rf FREQUENCY SYNTHESIZER
C L values. The shunt load capacitance, C L , presented across the crystal can be estimated to be: CL = where Cin = Cout = Ca = CO = CinCout + Ca + Co + C1 * C2 C1 + C2 Cin + Cout
5 pF (see Figure 11) 6 pF (see Figure 11) 1 pF (see Figure 11) the crystal's holder capacitance (see Figure 12) C1 and C2 = external capacitors (see Figure 10)
Ca Cin Cout
Figure 11. Parasitic Capacitances of the Amplifier
RS 1 2 1 LS CS 2
CO 1 Re Xe 2
NOTE: Values are supplied by crystal manufacturer (parallel resonant crystal).
Figure 12. Equivalent Crystal Networks The oscillator can be "trimmed" on-frequency by making a portion or all of C1 variable. The crystal and associated components must be located as close as possible to the OSCin and OSCout pins to minimize distortion, stray capacitance, stray inductance, and startup stabilization time. In some cases, stray capacitance should be added to the value for Cin and Cout. Power is dissipated in the effective series resistance of the crystal, Re, in Figure 12. The drive level specified by the crystal manufacturer is the maximum stress that a crystal can withstand without damage or excessive shift in frequency. R1 in Figure 10 limits the drive level. The use of R1 may not be necessary in some cases (i.e., R1 = 0 ). To verify that the maximum dc supply voltage does not overdrive the crystal, monitor the output frequency as a function of voltage at OSCout. (Care should be taken to minimize loading.) The frequency should increase very slightly as the dc supply voltage is increased. An overdriven crystal will decrease in frequency or become unstable with an increase in supply voltage. The operating supply voltage must be reduced or R1 must be increased in value if the overdriven condition exists. The user should note that the oscillator start-up time is proportional to the value of R1. Through the process of supplying crystals for use with CMOS inverters, many crystal manufacturers have developed expertise in CMOS oscillator design with crystals. Discussions with such manufacturers can prove very helpful (see Table 1).
OSCin
R1* C2
OSCout
C1
* May be deleted in certain cases. See text.
Figure 10. Pierce Crystal Oscillator Circuit For VDD = 5.0 V, the crystal should be specified for a loading capacitance, CL, which does not exceed 32 pF for frequencies to approximately 8.0 MHz, 20 pF for frequencies in the area of 8.0 to 15 MHz, and 10 pF for higher frequencies. These are guidelines that provide a reasonable compromise between IC capacitance, drive capability, swamping variations in stray and IC input/output capacitance, and realistic
MOTOROLA
MC145151-2 through MC145158-2
21
Table 1. Partial List of Crystal Manufacturers
Motorola -- Internet Address http://motorola.com United States Crystal Corp. Crystek Crystal Statek Corp. Fox Electronics NOTE: Motorola cannot recommend one supplier over another and in no way suggests that this is a complete listing of crystal manufacturers. (Search for resonators)
RECOMMENDED READING
Technical Note TN-24, Statek Corp. Technical Note TN-7, Statek Corp. E. Hafner, "The Piezoelectric Crystal Unit - Definitions and Method of Measurement", Proc. IEEE, Vol. 57, No. 2 Feb., 1969. D. Kemper, L. Rosine, "Quartz Crystals for Frequency Control", Electro-Technology, June, 1969. P. J. Ottowitz, "A Guide to Crystal Selection", Electronic Design, May, 1966.
DESIGN GUIDELINES The system total divide value, Ntotal (NT) will be dictated by the application: NT = frequency into the prescaler =NP+A frequency into the phase detector
DUAL-MODULUS PRESCALING
OVERVIEW The technique of dual-modulus prescaling is well established as a method of achieving high performance frequency synthesizer operation at high frequencies. Basically, the approach allows relatively low-frequency programmable counters to be used as high-frequency programmable counters with speed capability of several hundred MHz. This is possible without the sacrifice in system resolution and performance that results if a fixed (single-modulus) divider is used for the prescaler. In dual-modulus prescaling, the lower speed counters must be uniquely configured. Special control logic is necessary to select the divide value P or P + 1 in the prescaler for the required amount of time (see modulus control definition). Motorola's dual-modulus frequency synthesizers contain this feature and can be used with a variety of dual-modulus prescalers to allow speed, complexity and cost to be tailored to the system requirements. Prescalers having P, P + 1 divide values in the range of / 3// 4 to / 128// 129 can be controlled by most Motorola frequency synthesizers. Several dual-modulus prescaler approaches suitable for use with the MC145152-2, MC145156-2, or MC145158-2 are:
MC12009 MC12011 MC12013 MC12015 MC12016 MC12017 MC12018 MC12028A MC12052A MC12054A / 5// 6 / 8// 9 / 10// 11 / 32// 33 / 40// 41 / 64// 65 / 128// 129 / 32/33 or / 64/65 / 64/65 or / 128/129 / 64/65 or / 128/129 440 MHz 500 MHz 500 MHz 225 MHz 225 MHz 225 MHz 520 MHz 1.1 GHz 1.1 GHz 2.0 GHz
N is the number programmed into the / N counter, A is the number programmed into the / A counter, P and P + 1 are the two selectable divide ratios available in the dual-modulus prescalers. To have a range of NT values in sequence, the / A counter is programmed from zero through P - 1 for a particular value N in the / N counter. N is then incremented to N + 1 and the / A is sequenced from 0 through P - 1 again. There are minimum and maximum values that can be achieved for NT. These values are a function of P and the size of the / N and / A counters. The constraint N A always applies. If Amax = P - 1, then Nmin P - 1. Then NTmin = (P - 1) P + A or (P - 1) P since A is free to assume the value of 0. NTmax = Nmax P + Amax To maximize system frequency capability, the dual-modulus prescaler output must go from low to high after each group of P or P + 1 input cycles. The prescaler should divide by P when its modulus control line is high and by P + 1 when its MC is low. For the maximum frequency into the prescaler (fVCOmax), the value used for P must be large enough such that: 1. fVCOmax divided by P may not exceed the frequency capability of fin (input to the / N and / A counters). 2. The period of fVCO divided by P must be greater than the sum of the times: a. Propagation delay through the dual-modulus prescaler. b. Prescaler setup or release time relative to its MC signal. c. Propagation time from fin to the MC output for the frequency synthesizer device. A sometimes useful simplification in the programming code can be achieved by choosing the values for P of 8, 16, 32, or 64. For these cases, the desired value of NT results when NT in binary is used as the program code to the / N and / A counters treated in the following manner: 1. Assume the / A counter contains "a" bits where 2a P. 2. Always program all higher order / A counter bits above "a" to 0.
MC145151-2 through MC145158-2
MOTOROLA
22
3. Assume the / N counter and the / A counter (with all the higher order bits above "a" ignored) combined into a single binary counter of n + a bits in length (n = number of divider stages in the / N counter). The MSB of this "hypothetical" counter is to correspond to the MSB of / N and
the LSB is to correspond to the LSB of / A. The system divide value, NT, now results when the value of NT in binary is used to program the "new" n + a bit counter. By using the two devices, several dual-modulus values are achievable (shown in Figure 13).
MC
DEVICE A DEVICE B DEVICE A MC12009 MC10131 / 20// 21 MC10138 / 50// 51
DEVICE B
MC12011 / 32// 33 / 80// 81
MC12013 / 40// 41 / 100// 101
NOTE: MC12009, MC12011, and MC12013 are pin equivalent. MC12015, MC12016, and MC12017 are pin equivalent.
Figure 13. Dual-Modulus Values
MOTOROLA
MC145151-2 through MC145158-2
23
PACKAGE DIMENSIONS
P SUFFIX PLASTIC DIP CASE 648-08 (MC145157-2, MC145158-D) -A-
16 9 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 5. ROUNDED CORNERS OPTIONAL. DIM A B C D F G H J K L M S INCHES MIN MAX 0.740 0.770 0.250 0.270 0.145 0.175 0.015 0.021 0.040 0.70 0.100 BSC 0.050 BSC 0.008 0.015 0.110 0.130 0.295 0.305 0_ 10 _ 0.020 0.040 MILLIMETERS MIN MAX 18.80 19.55 6.35 6.85 3.69 4.44 0.39 0.53 1.02 1.77 2.54 BSC 1.27 BSC 0.21 0.38 2.80 3.30 7.50 7.74 0_ 10 _ 0.51 1.01
B
1 8
F S
C
L
-T- H G D
16 PL
SEATING PLANE
K
J TA
M
M
0.25 (0.010)
M
P SUFFIX PLASTIC DIP CASE 710-02 (MC145151-2, MC145152-2)
NOTES: 1. POSITIONAL TOLERANCE OF LEADS (D), SHALL BE WITHIN 0.25mm (0.010) AT MAXIMUM MATERIAL CONDITION, IN RELATION TO SEATING PLANE AND EACH OTHER. 2. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 3. DIMENSION B DOES NOT INCLUDE MOLD FLASH. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 36.45 37.21 13.72 14.22 3.94 5.08 0.36 0.56 1.02 1.52 2.54 BSC 1.65 2.16 0.20 0.38 2.92 3.43 15.24 BSC 0 15 0.51 1.02 INCHES MIN MAX 1.435 1.465 0.540 0.560 0.155 0.200 0.014 0.022 0.040 0.060 0.100 BSC 0.065 0.085 0.008 0.015 0.115 0.135 0.600 BSC 0 15 0.020 0.040
28
15
B
1 14
A N
C
L
H
G F D
K
SEATING PLANE
M
J
MC145151-2 through MC145158-2
MOTOROLA
24
DW SUFFIX SOG PACKAGE CASE 751F-04 (MC145151-2, MC145152-2) -A28 15 14X
-B1 14
P 0.010 (0.25)
M
B
M
28X D
0.010 (0.25)
M
TA
S
B
S
M R X 45
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF D DIMENSION AT MAXIMUM MATERIAL CONDITION. DIM A B C D F G J K M P R MILLIMETERS MIN MAX 17.80 18.05 7.60 7.40 2.65 2.35 0.49 0.35 0.90 0.41 1.27 BSC 0.32 0.23 0.29 0.13 8 0 10.05 10.55 0.75 0.25 INCHES MIN MAX 0.701 0.711 0.292 0.299 0.093 0.104 0.014 0.019 0.016 0.035 0.050 BSC 0.009 0.013 0.005 0.011 8 0 0.395 0.415 0.010 0.029
-T26X
C G K -TSEATING PLANE
F J
DW SUFFIX SOG PACKAGE CASE 751G-02 (MC145157-2, MC145158-2) -A-
16 9 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF D DIMENSION AT MAXIMUM MATERIAL CONDITION. MILLIMETERS MIN MAX 10.15 10.45 7.40 7.60 2.35 2.65 0.35 0.49 0.50 0.90 1.27 BSC 0.25 0.32 0.10 0.25 0_ 7_ 10.05 10.55 0.25 0.75 INCHES MIN MAX 0.400 0.411 0.292 0.299 0.093 0.104 0.014 0.019 0.020 0.035 0.050 BSC 0.010 0.012 0.004 0.009 0_ 7_ 0.395 0.415 0.010 0.029
-B-
1 8
8X
P 0.010 (0.25)
M
B
M
16X
D
M
J TA
S
0.010 (0.25)
B
S
F R X 45 _ C -T-
14X DIM A B C D F G J K M P R
G
K
SEATING PLANE
M
MOTOROLA
MC145151-2 through MC145158-2
25
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 1-303-675-2140 or 1-800-441-2447 Customer Focus Center: 1-800-521-6274 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 1-602-244-6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, Motorola Fax Back System - US & Canada ONLY 1-800-774-1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298 - http://sps.motorola.com/mfax/ HOME PAGE: http://motorola.com/sps/ JAPAN: Motorola Japan Ltd.; SPD, Strategic Planning Office, 141, 4-32-1 Nishi-Gotanda, Shinagawa-ku, Tokyo, Japan. 81-3-5487-8488
MC145151-2 through MC145158-2 26
MC145151-2/D MOTOROLA

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